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EV Powertrain Simulations in Saber
- 1. Alan Courtay
October 29, 2015
Paris Saber Seminar, La Defense
Modeling of PMSM Motor Drive
Multi Time Scale Analysis with Saber
- 2. © 2015 Synopsys, Inc. 2
Simplified Electric Vehicle Powertrain
Modeled after Market Available Electric Vehicle
Published
PMSM Electric Motor Max power / torque: 80 kW / 280 Nm
Li-Ion Battery
Total energy: 24 kWh
Max power > 90 kW
Number of cells: 192 (2 parallel, 96 series)
Cell voltage: 3.8 V
Nominal system voltage: 364.8 V
Gear Ratio 1/7.94
Curb Weight 1521 kg
0-100 km/h ~ 10 sec
Drag Coefficient 0.28
Inverter Frequency 5 kHz
Assumed
PMSM Electric Motor Max power / torque: 100 kW / 178 Nm, 8 poles
Inverter Efficiency 90%
Gear Efficiency 97%
Wheel Radius 0.3 m
- 3. © 2015 Synopsys, Inc. 3
Simplified Electric Vehicle Powertrain
Modeled after Market Available Electric Vehicle
Published
PMSM Electric Motor Max power / torque: 80 kW / 280 Nm
Li-Ion Battery
Total energy: 24 kWh
Max power > 90 kW
Number of cells: 192 (2 parallel, 96 series)
Cell voltage: 3.8 V
Nominal system voltage: 364.8 V
Gear Ratio 1/7.94
Curb Weight 1521 kg
0-100 km/h ~ 10 sec
Drag Coefficient 0.28
Inverter Frequency 5 kHz
Assumed
PMSM Electric Motor Max power / torque: 100 kW / 178 Nm, 8 poles
Inverter Efficiency 90%
Gear Efficiency 97%
Wheel Radius 0.3 m
IPMSM model from
JMAG-RT Motor Model
Library
- 4. © 2015 Synopsys, Inc. 4
1
2
3
4• Level 1
– Behavioral Li-Ion battery
– Dynamic thermal dq inverter and PMSM
– Thermal network
• Level 2
– Average/non-switching inverter /w TLU losses
– LdLq or detailed FEA-based PMSM
• Level 3
– Ideal switch inverter /w TLU losses
• Level 4
– Improved datasheet-driven IGBT1
Abstraction Levels
- 7. © 2015 Synopsys, Inc. 7
1
ia,va
ib,vb
ic,vc
a
b
c
Sinusoidal currents and switching/PWM voltages are abstracted to only
retain phase and amplitude of signals in synchronous reference frame
iq
id
vq
vd
i
v
- 8. © 2015 Synopsys, Inc. 8
1
FEA-based look-up tables used for
flux saturation Ld(id) and Lq(iq), and
speed/current dependent iron loss
- 12. © 2015 Synopsys, Inc. 12
1Reluctance Torque
Br
Hc
m
The permanent magnets have low
permeability / high reluctance (~ air
gap). The rotor orients itself in the
position of least flux resistance.
- 14. © 2015 Synopsys, Inc. 14
Switching Losses
1
≈ 𝛼 ∙ 𝒗 𝒐𝒇𝒇 ∙ 𝒊 𝒐𝒏
on+off
𝑷 𝒔𝒘 = 𝑬 𝒔𝒘 ∙ 𝒇 𝒔
= 𝑬 𝒔𝒘 (𝒗 𝒐𝒇𝒇, 𝒊 𝒐𝒏)
rec+
𝒊 𝒐𝒏 (𝑨) 𝒗 𝒐𝒇𝒇 (𝑽)
𝑬 𝒔𝒘 (𝑱)
- 15. © 2015 Synopsys, Inc. 15
v
i
one 1D look-up table: 𝑃 𝑐(𝑖) = 𝑖. 𝑣(𝑖)
Conduction Losses
1
- 17. © 2015 Synopsys, Inc. 17
1
𝑖∗2
= 𝑖 𝑑
∗2
+ 𝑖 𝑞
∗2
𝜕𝑇
𝜕𝑖∗ = 0
𝑖 𝑑
∗
=
𝜑 𝑚 − 𝜑 𝑚
2 + 8 𝐿 𝑞 − 𝐿 𝑑
2
𝑖∗2
4 𝐿 𝑞 − 𝐿 𝑑
𝑖 𝑞
∗
= 𝑠𝑔𝑛(𝑖∗) 𝑖∗2
− 𝑖 𝑑
∗2
Maximum Torque Per Amp
𝑖 𝑑
∗
𝑖 𝑞
∗
𝑖∗
Field Oriented ControlField Oriented Control
MTPA 𝑖∗
𝑖 𝑑
∗
𝜃𝑖
𝑖 𝑞
∗
𝑖 𝑑
𝑖 𝑞
- 18. © 2015 Synopsys, Inc. 18
1Flux Weakening
𝑖 𝑑
∗
𝑖 𝑞
∗
𝑖 𝑑
𝑖 𝑞
Field Oriented Control
- 19. © 2015 Synopsys, Inc. 19
1Flux Weakening
𝑖 𝑑
∗
𝑖 𝑞
∗
𝑖 𝑑
𝑖 𝑞
Field Oriented Control
𝑉𝑞 = 𝑅𝑖 𝑞 + 𝐿 𝑞
𝑑𝑖 𝑞
𝑑𝑡
+ 𝜔 𝐿 𝑑 𝑖 𝑑 + 𝜑 𝑚
𝑉𝑑 = 𝑅𝑖 𝑑 + 𝐿 𝑑
𝑑𝑖 𝑑
𝑑𝑡
− 𝜔𝐿 𝑞 𝑖 𝑞
𝑇 =
3
4
𝑝 𝜑 𝑚 𝑖 𝑞 + 𝐿 𝑑 − 𝐿 𝑞 𝑖 𝑑 𝑖 𝑞
R neglected,
steady-state
- 20. © 2015 Synopsys, Inc. 20
1Flux Weakening
𝑖 𝑑
∗
𝑖 𝑞
∗
𝑖 𝑑
𝑖 𝑞
Field Oriented Control
𝑉𝑞 = 𝜔 𝐿 𝑑 𝑖 𝑑 + 𝜑 𝑚
𝑉𝑑 = −𝜔𝐿 𝑞 𝑖 𝑞
𝑇 =
3
4
𝑝 𝜑 𝑚 𝑖 𝑞 + 𝐿 𝑑 − 𝐿 𝑞 𝑖 𝑑 𝑖 𝑞
At high speed, back-EMF
exceeds DC link voltage
- 21. © 2015 Synopsys, Inc. 21
1Flux Weakening
𝑖 𝑑
∗
𝑖 𝑞
∗
𝑖 𝑑
𝑖 𝑞
Field Oriented Control
𝑉𝑞 = 𝜔 𝐿 𝑑 𝑖 𝑑 + 𝜑 𝑚
𝑉𝑑 = −𝜔𝐿 𝑞 𝑖 𝑞
𝑇 =
3
4
𝑝 𝜑 𝑚 𝑖 𝑞 + 𝐿 𝑑 − 𝐿 𝑞 𝑖 𝑑 𝑖 𝑞
Increase current angle (negative
component of id) to “weaken”
magnet flux and reduce back-EMF
- 22. © 2015 Synopsys, Inc. 22
𝑖 𝑑
∗
𝑖 𝑞
∗
𝑖 𝑑
𝑖 𝑞
Field Oriented Control
MTPA 𝑖
−
𝜑 𝑚
𝐿 𝑑
𝜑 𝑚
𝐿 𝑞 − 𝐿 𝑑
𝑖 𝑞
𝑖 𝑑
1Flux Weakening
𝑉𝑞 = 𝜔 𝐿 𝑑 𝑖 𝑑 + 𝜑 𝑚
𝑉𝑑 = −𝜔𝐿 𝑞 𝑖 𝑞
𝑇 =
3
4
𝑝 𝜑 𝑚 𝑖 𝑞 + 𝐿 𝑑 − 𝐿 𝑞 𝑖 𝑑 𝑖 𝑞
Increase current angle (negative
component of id) to “weaken”
magnet flux and reduce back-EMF
𝑣2
= 𝑣 𝑑
2
+ 𝑣 𝑞
2
Voltage Limit Ellipse
𝑣2
𝜔2
= 𝐿 𝑑 𝑖 𝑑 + 𝜑 𝑚
2
+ 𝐿 𝑞
2
𝑖 𝑞
2
𝜃𝑖
- 23. © 2015 Synopsys, Inc. 23
𝑖 𝑑
∗
𝑖 𝑞
∗
𝑖 𝑑
𝑖 𝑞
Field Oriented Control
MTPA
𝑖
−
𝜑 𝑚
𝐿 𝑑
𝜑 𝑚
𝐿 𝑞 − 𝐿 𝑑
Increasing Speed
𝑖 𝑞
𝑖 𝑑
1Flux Weakening
𝑉𝑞 = 𝜔 𝐿 𝑑 𝑖 𝑑 + 𝜑 𝑚
𝑉𝑑 = −𝜔𝐿 𝑞 𝑖 𝑞
𝑇 =
3
4
𝑝 𝜑 𝑚 𝑖 𝑞 + 𝐿 𝑑 − 𝐿 𝑞 𝑖 𝑑 𝑖 𝑞
Increase current angle (negative
component of id) to “weaken”
magnet flux and reduce back-EMF
𝜃𝑖
𝑣2
= 𝑣 𝑑
2
+ 𝑣 𝑞
2
Voltage Limit Ellipse
𝑣2
𝜔2
= 𝐿 𝑑 𝑖 𝑑 + 𝜑 𝑚
2
+ 𝐿 𝑞
2
𝑖 𝑞
2
- 24. © 2015 Synopsys, Inc. 24
1
Field Oriented Control
𝑉𝑞 = 𝜔 𝐿 𝑑 𝑖 𝑑 + 𝜑 𝑚
𝑉𝑑 = −𝜔𝐿 𝑞 𝑖 𝑞
𝑇 =
3
4
𝑝 𝜑 𝑚 𝑖 𝑞 + 𝐿 𝑑 − 𝐿 𝑞 𝑖 𝑑 𝑖 𝑞
Feedforward Compensation
- 25. © 2015 Synopsys, Inc. 25
1• Analyze system efficiency over long driving cycles
• Evaluate energy flow in critical regimes
(deceleration, braking)
• Handle power dissipation and cooling
• Design stable motor control (e.g. FOC)
- 26. © 2015 Synopsys, Inc. 26
1• Analyze system efficiency over long driving cycles
• Evaluate energy flow in critical regimes
(deceleration, braking)
• Handle power dissipation and cooling
• Design stable motor control (e.g. FOC)
- 27. © 2015 Synopsys, Inc. 27
1
2
Sinusoidal currents and voltages (no switching)
- 28. © 2015 Synopsys, Inc. 28
1
2
a
b
c
𝜃 𝑚
𝜃𝑖
i
Accounts for
1. Mutual coupling between phases
2. Flux saturation
3. Spatial harmonics
- 29. © 2015 Synopsys, Inc. 29
1
2
• Analyze system dynamics
• Evaluate energy flow in critical regimes
(deceleration, braking)
• Design stable motor control (e.g. FOC)
• Evaluate torque ripples
Motor
Torque
Regenerative
Braking
Sloped Terrain Startup
- 30. © 2015 Synopsys, Inc. 30
1
2
• Analyze system dynamics
• Evaluate energy flow in critical regimes
(deceleration, braking)
• Design stable motor control (e.g. FOC)
• Evaluate torque ripples
Torque ripples due to
spatial harmonics
- 31. © 2015 Synopsys, Inc. 31
1
2
3
• Design PWM control (e.g. compensate dead time distortion)
• Mitigate faults in critical regimes (e.g. in flux weakening mode)
Dead time distortion
(corrected and uncorrected)
- 32. © 2015 Synopsys, Inc. 32
1
2
3
4
• Optimize gate drive tradeoff losses vs. EMI noise
• Control current/voltage overshoot
• Prevent accidental turn-on
𝑖 = 𝐶𝑐𝑔 ∙
𝑑𝑉𝑐𝑒
𝑑𝑡
≫ 1
Vg < Vge(th)
Rg
Vgei > Vge(th)
c
e
𝑉 = 𝐿 𝑒 ∙
𝑑𝑖 𝑐
𝑑𝑡
≪ −1
Accidental turn-on
mechanisms
- 33. © 2015 Synopsys, Inc. 33
2016.03 IGBT Tool
• Improved matching of transient
characteristics
– Cge made non-linear
– Control of turn-off voltage oscillations
– Decoupling between turn-on and turn-off
• Easier characterization
– Optimizer at most steps, including
transient characteristics
– Turn-on and turn-off characteristics
combined in one view
– Improved DC anchor points
– Library of pre-characterized components
– Numerous bug fixes
- 34. © 2015 Synopsys, Inc. 34
IGBT Principle
Collector/Anode
Emitter/Cathode
P+ Emitter
Gate
P
N- Base
P+
N+
• Two junctions
– J1 space charge region develops
when Vce < 0
– J2 space charge region develops
when Vce > 0 and Vge < Vge(th)
– Wide and low doped N- base region
→ large blocking voltage
• BJT+MOSFET
– Insulated gate → voltage control
– Holes injected from P+ emitter →
conductivity modulation
– High forward conduction current
density: 𝑖 𝑐 = 𝑖 𝑚𝑜𝑠 + 𝑖 𝑝
• Slow removal of carriers in the
base → longer switching time
during turn-off and tail current
J1
J2
+
+
- 35. © 2015 Synopsys, Inc. 35
IGBT Principle
Collector/Anode
Emitter/Cathode
P+ Emitter
Gate
P
N- Base
Rb
PNP
N-MOS
P+
N+
imos ip
(𝛽)
++
+
holes
electrons
• Two junctions
– J1 space charge region develops
when Vce < 0
– J2 space charge region develops
when Vce > 0 and Vge < Vge(th)
– Wide and low doped N- base region
→ large blocking voltage
• BJT+MOSFET
– Insulated gate → voltage control
– Holes injected from P+ emitter →
conductivity modulation
– High forward conduction current
density: 𝑖 𝑐 = 𝑖 𝑚𝑜𝑠 + 𝑖 𝑝
• Slow removal of carriers in the
base → longer switching time
during turn-off and tail current
- 36. © 2015 Synopsys, Inc. 36
IGBT Principle
Collector/Anode
Emitter/Cathode
P+ Emitter
Gate
P
N- Base
P+
N+
imos ip+
+
• Two junctions
– J1 space charge region develops
when Vce < 0
– J2 space charge region develops
when Vce > 0 and Vge < Vge(th)
– Wide and low doped N- base region
→ large blocking voltage
• BJT+MOSFET
– Insulated gate → voltage control
– Holes injected from P+ emitter →
conductivity modulation
– High forward conduction current
density: 𝑖 𝑐 = 𝑖 𝑚𝑜𝑠 + 𝑖 𝑝
• Slow removal of carriers in the
base → longer switching time
during turn-off and tail current
- 37. © 2015 Synopsys, Inc. 37
IGBT Principle
Collector/Anode
Emitter/Cathode
P+ Emitter
Gate
P
N- Base
P+
N+
+• Two junctions
– J1 space charge region develops
when Vce < 0
– J2 space charge region develops
when Vce > 0 and Vge < Vge(th)
– Wide and low doped N- base region
→ large blocking voltage
• BJT+MOSFET
– Insulated gate → voltage control
– Holes injected from P+ emitter →
conductivity modulation
– High forward conduction current
density: 𝑖 𝑐 = 𝑖 𝑚𝑜𝑠 + 𝑖 𝑝
• Slow removal of carriers in the
base → longer switching time
during turn-off and tail current
- 42. © 2015 Synopsys, Inc. 42
Ic
Vcc
Inductive Clamp Test Circuit
Vcc
Rg(off)
Vg(on)
Vg(off)
Lp
DUT
(IGBT)
-15V
Ic
DUT
(Diode)
Rg(on)
Vg(on)
- 43. © 2015 Synopsys, Inc. 43
11
1
1
2
2
2
2
3
3
3
3
4
4
4
4
5
5
5
5
𝐶𝑟𝑒𝑠 = 𝐶𝑔𝑐
𝐶𝑖𝑒𝑠 = 𝐶𝑔𝑐 + 𝐶𝑔𝑒
𝐶𝑜𝑒𝑠 = 𝐶𝑔𝑐 + 𝐶𝑐𝑒
- 44. © 2015 Synopsys, Inc. 44
𝐶𝑟𝑒𝑠 = 𝐶𝑔𝑐
𝐶𝑖𝑒𝑠 = 𝐶𝑔𝑐 + 𝐶𝑔𝑒
𝐶𝑜𝑒𝑠 = 𝐶𝑔𝑐 + 𝐶𝑐𝑒
Cies = dQg / dVgs
Miller plateau Vgs
~1.2nF
~1.2nF
- 48. © 2015 Synopsys, Inc. 48
IKW75N65EL5
Thermal Characteristics
Cauer networkFoster network
Duty cycle zero
sufficient to match
the other curvesOnly physical if
connected to
temperature source
- 49. © 2015 Synopsys, Inc. 49
Future Work
• Merging of MOSFET and IGBT
tools
• Improve DC characteristics for
SiC MOSFET’s
• sw1_l4 and pwld with accurate
switching losses (TLU)
• Battery characterization tool
(with enhanced model)
NXP TrenchMOS BUK9640-100A